Circuits for efficient detection of vector signaling codes for chip-to-chip communication

ABSTRACT

In a detection circuit, inputs correspond to received indications of vector signaling code words received by a first integrated circuit from a second integrated circuit. With four inputs, the circuit compares a first pair to obtain a first difference result and compares a second pair, disjoint from the first pair, to obtain a second difference result. The first and second difference results are then summed to form an output function. A system might use a plurality of such detection circuits to arrive at an input word. The circuit can include amplification, equalization, and input selection with efficient code word detection. The vector signaling code can be a Hadamard matrix code encoding for three input bits. The circuit might also have frequency-dependent gain, a selection function that directs one of the summation function result or the first difference result to the output function, variable gain, and/or a slicer.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. application Ser. No.15/812,917, filed Nov. 14, 2017, entitled “Circuits for EfficientDetection of Vector Signaling Codes for Chip-to-Chip Communication”,which is a continuation of U.S. application Ser. No. 15/271,065, filedSep. 20, 2016, entitled “Circuits for Efficient Detection of VectorSignaling Codes for Chip-to-Chip Communication,” which is a continuationof U.S. application Ser. No. 15/070,911, filed Mar. 15, 2016, entitled“Circuits for Efficient Detection of Vector Signaling Codes ForChip-to-Chip Communication Using Sums of Differences,” which is acontinuation of U.S. application Ser. No. 13/895,206 filed May 15, 2013,entitled “Circuits for Efficient Detection of Vector Signaling Codes ForChip-to-Chip Communication Using Sums of Differences”, all of which arehereby incorporated herein by reference in their entirety.

REFERENCES

The following references are herein incorporated by reference in theirentirety for all purposes:

U.S. Patent Publication No. 2011/0268225 of application Ser. No.12/784,414, filed May 20, 2010, naming Harm Cronie and Amin Shokrollahi,entitled “Orthogonal Differential Vector Signaling” (hereinafter “CronieI”);

U.S. Patent Publication No. 2011/0302478 of application Ser. No.12/982,777, filed Dec. 30, 2010, naming Harm Cronie and AminShokrollahi, entitled “Power and Pin Efficient Chip-to-ChipCommunications with Common-Mode Resilience and SSO Resilience”(hereinafter “Cronie II”);

U.S. patent application Ser. No. 13/030,027, filed Feb. 17, 2011, namingHarm Cronie, Amin Shokrollahi and Armin Tajalli, entitled “Methods andSystems for Noise Resilient, Pin-Efficient and Low Power Communicationswith Sparse Signaling Codes” (hereinafter “Cronie III”).

U.S. patent application Ser. No. 13/463,742, filed May 3, 2012, namingHarm Cronie and Amin Shokrollahi, entitled “Finite State Encoders andDecoders for Vector Signaling Codes” (hereinafter called “Cronie IV”).

U.S. patent application Ser. No. 13/844,331, filed Mar. 15, 2013, namingHarm Cronie and Brian Holden, entitled “Sorting Decoder” (hereinaftercalled “Cronie V”.)

U.S. patent application Ser. No. 13/603,107, filed Sep. 4, 2012, namingBrian Holden and Amin Shokrollahi, entitled “Methods and Systems forSelection of Unions of Vector Signaling Codes for Power and PinEfficient Chip-to-Chip Communication” (hereinafter “Holden I”).

U.S. patent application Ser. No. 13/842,740, filed Mar. 15, 2013, namingBrian Holden, Amin Shokrollahi, and Anant Singh, entitled “Methods andSystems for Skew Tolerance in and Advanced Detectors for VectorSignaling Codes for Chip-to-Chip Communication” (hereinafter “HoldenII”).

TECHNICAL FIELD

The present invention relates to communications in general and inparticular to the transmission of signals capable of conveyinginformation and detection of those signals in chip-to-chipcommunication.

BACKGROUND

In communication systems, a goal is to transport information from onephysical location to another. It is typically desirable that thetransport of this information is reliable, is fast and consumes aminimal amount of resources. One common information transfer medium isthe serial communications link, which may be based on a single wirecircuit relative to ground or other common reference, multiple suchcircuits relative to ground or other common reference, or multiplecircuits used in relation to each other. A common example of the latteruses differential signaling (“DS”). Differential signaling operates bysending a signal on one wire and the opposite of that signal on amatching wire. The signal information is represented by the differencebetween the wires, rather than their absolute values relative to groundor other fixed reference.

There are a number of signaling methods that maintain the desirableproperties of DS while increasing pin efficiency over DS. Vectorsignaling is a method of signaling. With vector signaling, a pluralityof signals on a plurality of wires is considered collectively althougheach of the plurality of signals might be independent. Each of thecollective signals is referred to as a component and the number ofplurality of wires is referred to as the “dimension” of the vector. Insome embodiments, the signal on one wire is entirely dependent on thesignal on another wire, as is the case with DS pairs, so in some casesthe dimension of the vector might refer to the number of degrees offreedom of signals on the plurality of wires instead of exactly thenumber of wires in the plurality of wires.

With binary vector signaling, each component or “symbol” of the vectortakes on one of two possible values. With non-binary vector signaling,each symbol has a value that is a selection from a set of more than twopossible values. Any suitable subset of a vector signaling code denotesa “subcode” of that code. Such a subcode may itself be a vectorsignaling code.

Some vector signaling methods are described in Cronie I, Cronie II,Cronie III, Cronie IV, and Cronie V. While non-binary vector signalingmethods can provide substantial improvements regarding the tradeoff ofpin efficiency, power efficiency and noise resilience as compared totraditional signaling methods, there are some applications whereinadditional improvements are possible, and sometimes necessary.

BRIEF SUMMARY

In a detection circuit, inputs correspond to received indications ofvector signaling code words received by a first integrated circuit froma second integrated circuit. In a preferred embodiment, the number ofinputs is four and the detection circuit compares a first pair of theinputs to obtain a first difference result and compares a second pair ofinputs, disjoint from the first pair of inputs, to obtain a seconddifference result. The first difference result and the second differenceresult are then summed to form an output function. A system might use aplurality of such detection circuits to arrive at an input word.

In one embodiment, each input is from the set {−1, −⅓, ⅓, 1}, the vectorsignaling code comprises the union of all permutations of the symbol set{1, −⅓, −⅓, −⅓} and all permutations of the symbol set {−1, ⅓, ⅓, ⅓},the system uses three of the detection circuits, and the eight possiblevector signaling code words encode for three input bits.

In accordance with at least one embodiment of the invention, circuitsand systems are described for the efficient reception and detection ofvector signal coded data transmitted over physical channels such thatthe signals transmitted are resilient to common mode noise, do notrequire a common reference at the transmission and reception points, andcan produce a higher pin efficiency than conventional differentialsignaling with relatively low power dissipation for encoding anddecoding. In some embodiments, different voltage, current, etc. levelsare used for signaling and more than two levels might be used, such as aternary sparse signaling code wherein each wire signal has one of threevalues. The decoder can be a 4×4 Hadamard matrix decoder to decode aHadamard matrix code with two differences/comparisons followed by asummation.

Hardware elements might be provided to provide storage for symbols ofinput information used for selecting code words, processing hardware toconvert symbols to signals, parsing symbols into separate partitions,storing results, and providing the partitions in sequence as signals.Various embodiments are given with reference to specific hardwareimplementations of small area and low power dissipation. In hardware, a“function” might be implemented using specific circuit elements, activeor passive, or might be implemented as a consequence of connections of acircuit interconnection. For example, a summation function might beimplemented by wiring two current sources in parallel to form athree-wire junction such that the current on one wire of the connectionis the sum (or inverse of the sum) of the currents on the other twowires. Alternatively, a particular circuit element could receive twophysical values and output their sum.

This Brief Summary is provided to introduce a selection of concepts in asimplified form that are further described below in the DetailedDescription. This Brief Summary is not intended to identify key oressential features of the claimed subject matter, nor is it intended tobe used as an aid in determining the scope of the claimed subjectmatter. Other objects and/or advantages of the present invention will beapparent to one of ordinary skill in the art upon review of the DetailedDescription and the included drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

Various embodiments in accordance with the present disclosure will bedescribed with reference to the drawings. Same numbers are usedthroughout the disclosure and figures to reference like components andfeatures.

FIG. 1 is a schematic diagram that depicts aspects of an examplemultiple wire communications channel utilizing encoding and decoding inaccordance with at least one embodiment of the invention.

FIGS. 2A, 2B and 2C are schematic diagrams of example differentialamplifier stage embodiments in accordance with the invention.

FIGS. 3A, 3B and 3C are schematic diagrams illustrating termination ofreceive inputs to a chip in accordance with at least one embodiment ofthe invention.

FIG. 4 is a schematic diagram of a circuit combining computationfunction, signal multiplexing, and adjustable gain and equalization orpeaking, in accordance with at least one embodiment of the invention.

FIG. 5 is a block diagram showing use of the termination network ofFIGS. 3A-3C and multiple instances of the circuit of FIG. 4 to provide acomplete receive input system, in accordance with at least oneembodiment of the invention.

FIG. 6 is a block diagram showing use of signal feedback in accordancewith at least one embodiment of the invention.

FIG. 7 is a schematic diagram of another circuit combining computationfunction signal multiplexing, and adjustable gain and equalization orpeaking, in accordance with at least one embodiment of the invention.

FIG. 8 is a table illustrating logical values that might appear atvarious points in a detector in accordance with at least one embodimentof the invention.

DETAILED DESCRIPTION

Conventional communications systems receivers operate on individualwires or communications channels (i.e., single-ended signaling) or onpairs of wires or communications channels (i.e., differentialsignaling). In either case, a received signal is detected by comparisonof a received value against a reference; for single-ended signaling, thereference may be a known voltage level such as ground or a calculated orpredetermined offset voltage, while a differential receiver detects thesignal of one wire in the pair in comparison to the signal of the otherwire in the pair.

Such communications channels may be extended to groups of wires carryingsignals that collectively represent an encoded value. FIG. 1 is a blockdiagram showing communications channel 140 connecting transmittingdevice 110 to receiving device 150 using an example a group of fourwires 145 to communicate source data 100 to destination 180 using avector signaling code produced by encoder 120 and interpreted by decoder170. Also shown are connectors 130, 131, line receiver 160 andconnectors 165, 166.

Holden I describes an enhancement to the vector signaling code techniquethat makes use of the observation that the balance between complementarysignals in a differential signaling channel need not be held exactly tozero. Thus, a vector signaling code may comprise the union of subcodes,each subcode being distinguishable by its unique nonzero code word sum.

Vector signaling code receivers may perform a first operation similar tothat of a conventional receiver, by making a first determination of thesymbol represented by the particular received signal of each wire orcommunications channel. However, complete detection of the vectorsignaling code can require identification not merely of the individualsymbols of that code, but of the particular code word represented by theset of symbols communicated as a group. A vector signaling code receiveris said to “detect” vector signaling code C if for each code word c, thereceiver produces a valid and unique result Sc, which may directlycorrespond to receive result R, or may produce R via a mappingoperation.

Holden II describes the use of weighted multi-input comparators fordetection of vector signaling codes. A weighted multi-input comparatorwith coefficients a0, a1, . . . , am−1 is a circuit that accepts as itsinput a vector (x0, x1, . . . , xm−1) and outputs the signals indicatedin Equation 1, with the definition of the sign-function being sign(x)=+1if x>0, sign(x)=−1 if x<0, and sign(x) is undefined if x=0.

Output=sign(a0*x0+ . . . +am−1*xm−1)  (Eqn. 1)

A collection of such comparators each having distinct sets of inputweights may serve as a detector for a vector signaling code.

Efficient Computational Element

In a detection circuit, inputs correspond to received indications ofvector signaling code words received by a first integrated circuit froma second integrated circuit. In a preferred embodiment, the number ofinputs is four and the detection circuit compares a first pair of theinputs to obtain a first difference result and compares a second pair ofinputs, disjoint from the first pair of inputs, to obtain a seconddifference result. The first difference result and the second differenceresult are then summed to form an output function. A system might use aplurality of such detection circuits to arrive at an input word.

In one embodiment, each input is from the set {−1, −⅓, ⅓, ⅓}, the vectorsignaling code comprises the union of all permutations of the symbol set{1, −⅓, −⅓, −⅓} and all permutations of the symbol set {−1, ⅓, ⅓, ⅓},the system uses three of the detection circuits, and the eight possiblevector signaling code words encode for three input bits.

With the detection circuit performing differences ahead of performingsummation, it becomes possible to provide for lowered distributedimpedance and better high frequency response. In part, this is a resultof capacitance appearing at lower impedance points rather than higherimpedance points.

In accordance with at least one embodiment of the invention, a codeherein referred to as “H4” is described. H4 is a balanced, non-sparsevector signaling code of four symbols, comprising the union of allpermutations of the symbol set {1, −⅓, −⅓, −⅓} and all permutations ofthe symbol set {−1, ⅓, ⅓, ⅓ }.

An efficient component of a detector for H4 code performs calculationsof the form shown in Equation 2 where J, K, L, M are variablesrepresenting the symbol values of the four input signals values.

R=(J+L)−(K+M)  (Eqn. 2)

It may be noted that applying three instances of Equation 2 withdifferent permutations of receive signal input values to the fourvariables is sufficient to detect each code word of H4. As one exampleand without limitation, the input permutations producing the threeresults R0, R1, R2 based on Equations 3, 4 and 5 are sufficient tounambiguously identify each code word of vector signaling code H4 asrepresented by receive signal input values A, B, C, D.

R0=(A+C)−(B+D)  (Eqn. 3)

R1=(C+D)−(A+B)  (Eqn. 4)

R2=(C+B)−(D+A)  (Eqn. 5)

Architecturally, it is convenient to perform such detection operationsat or near the receiver input, and high speed capability requires anefficient, high performance embodiment.

FIG. 2A is a schematic diagram of one example circuit performing therequired calculation. It will be readily apparent to one familiar withthe art that the difference of two sums function of Equation 2 may beregrouped using the associative rule into an equivalent form comprisinga sum of two differences. These regrouped forms of Equations 3, 4, and 5are shown as Equations 6, 7, and 8.

R0=(A−B)+(C−D)  (Eqn. 6)

R1=(C−A)+(D−B)  (Eqn. 7)

R2=(C−D)+(B−A)  (Eqn. 8)

FIG. 8 is a table illustrating logical values that might appear atvarious points in a detector in accordance with at least one embodimentof the invention as represented by the equations above. It should beunderstood that this is but one example of an implementation or a fewvariations thereof.

The four circuit inputs of FIG. 2A are labeled J, K, L, M as at 201, andthe inputs are gate inputs to differential transistor pairs 230 and 235,each transistor pair herein referred to as a differential amplifier.These differential amplifiers share load resistors 220 providing thenecessary sum function, with the inherent differential function withineach of differential amplifier 230 and 235 providing the necessarydifference elements. Thus, the complimentary outputs labeled out andoutb at 240 represent the result of Equation 6, as an example, based oninputs J, K, L, M. Splitting the conventional current sink perdifferential pair into individual per-transistor current sinks 238allows introduction of resistors 236 and capacitors 237 that provide afrequency-dependent gain characteristic for line equalization orpeaking.

FIG. 2B is a schematic diagram of another embodiment of the invention.In this design, resistors 256 and capacitors 257 connect from the sourceof each transistor to a common node 258, providing a desirablefrequency-dependent gain characteristic for equalization or signalpeaking.

FIG. 2C is a schematic diagram of a further embodiment of the invention,where the common node 278 is used as a common connection to singlecurrent sink 290, rather than the multiple current sinks of FIG. 2B.Capacitors 276 are shown connecting between each transistor drain toground, with capacitors 276 and resistors 275 again providing adesirable frequency-dependent gain characteristic for equalization orpeaking.

It will be apparent to one skilled in the art that the functionalequivalent of Equation 2, including specific examples such asillustrated by Equations. 6, 7, and 8, may be embodied by any of thecircuits of FIGS. 2A-2C, given an appropriate mapping of receive signalinput values A, B, C, D to circuit inputs J, K, L, M. It will also beapparent that the described circuit topology may be applied to computeequivalent detection functions for codes other than the example H4 code.

In at least one embodiment of the invention as represented in eachschematic of FIGS. 2A-2C, one or both of the resistors and capacitorsdescribed as providing equalization or signal peaking are trimmable orvariable, allowing the amplification and equalization or peakingcharacteristics to be adjusted. The initial value or adjusted value ofthe capacitors may include zero, without limitation. Load resistors 220may be replaced by current sources, by current sources controlled by acommon mode feedback, or by a combination of resistors and inductors toprovide additional high-frequency peaking.

On-Chip Receive Signal Termination

At contemplated signal rates, conventional best practice might be toprovide matched transmission line termination for current mode logic(CML) receive input signals. Examples in accordance with at least oneembodiment of the invention are shown in FIGS. 3A-3C.

In FIG. 3A, signal inputs 301 labeled inputs a, b, c, and d areillustrated with external blocking capacitors 310, which optionally maybe used to prevent DC current flow over the interconnection. Thepresence of impedance anomalies such as bond wires and bonding pads issuggested at 315, representing such known sources of signal degradationat high data rates.

In at least one embodiment, the same circuitry used for vector signalingcode detection over example inputs a, b, c, d, also provides “legacymode” support for, as an example, differential signal reception on thesame inputs. Such selection of “legacy mode” may require support forgreater signal level inputs (as those signals may be provided bydifferent or earlier-generation components), and this extended-rangeinput support may be obtained by attenuating large signal inputs beforesubsequent processing, as examples ah, bh, ch, dh at 335.

To provide this attenuation function, the termination resistance 320 isshown comprising components 321 and 322; as one example, they representidentical resistive values summing to the required termination impedancewhile also providing an attenuated output within allowable on-chipsignal levels. Thus, signals 330 labeled a, b, c, d represent the fullinput signal level, while signals 335 labeled ah, bh, ch, dh represent,continuing the example, the same values attenuated to half amplitude.Subsequent processing circuits may select either full input signals orattenuated signals using, as an example, an analog multiplexer. Thevalues of 321 and 322 need not be identical, and in some embodiments maybe adjustable or trimmable, as illustrated by 322 of FIGS. 3A-3C.

Other embodiments in accordance with the invention utilize equivalentattenuator topologies known in the art, including so-called “T” and “PI”configurations, or eschew attenuation and combine elements 321 and 322into a single resistive termination. One alternative embodiment oftermination resistance 320 is shown in FIG. 3B, where components 321 and322 provide the desired attenuation ratio, and component 323 is trimmedor adjusted to obtain the desired termination impedance.

In FIGS. 3A and 3B, all terminations 320 connect to common mode biassource 340 and common mode filter capacitor 345. The bias voltageprovided by source 340 to subsequent active circuits can be circuit- andprocess-dependent; one typical value is 600 mV.

Another embodiment is illustrated in FIG. 3C, which provideslevel-shifting where blocking capacitor 310 is not used. Rather thanutilizing a common bias source 340, the common termination node iscoupled to ground via common mode filter capacitor 345, which may beshared across all terminations 320. The individual full-level andattenuated outputs are obtained through RF pass capacitors 385 and biasresistors 395, with the bias level of the receiver inputs set by currentsource 341 flow through the resistive path of 395 and 320.

Combined Multiplexer and Computation Element

A described computational circuit as in any of FIGS. 2A-2C may beintegrated with the suggested multiplexer function, as shown in theexample circuit of FIG. 4. This example comprises three components; thefirst selects between the difference of inputs J and K, or thedifference of attenuated inputs Jh and Kh; the second performs thecomputation of Equation 2 on inputs J, K, L, M, or provides internalloopback of this chip's transmit signals; and the final element selectsbetween the outputs of the first or of the second components.

This staged topology has been found to minimize loading effects, thusproviding optimum performance for the given process technology. Theresults allow embodiment of legacy mode operation with either attenuatedinput signals or full level input signals, an internal signal test mode,and/or vector signaling code detection.

Selectively enabling or disabling pairs of current sinks using thecontrol signals Enab 1 through Enab6 controls the multiplexer. Asexamples, inputs a and b may be selected instead of inputs ah and bh byenabling current sinks using Enab 1 and disabling current sinks usingEnab2, and then further selected by enabling current sinks using Enab5and disabling current sinks using Enab6 to, as an example, support alegacy mode differential receiver behavior. Conversely, selection of thecomputed function based on inputs a, b, c, d may be selected by enablingcurrent sinks using Enab3 and Enab4, and further selected by disablingcurrent sinks using Enab5 and enabling current sinks using Enab6.

One embodiment incorporates a test mode loopback of local transmitsignals, which may be obtained by enabling pass transistors 470 usingcontrol signal Enab7. It will be apparent to a practitioner of the artthat this multiplexer may also be used for other input selections,including alternative mappings of wire signals to computed functioninputs and/or a different computed function.

Inputs to an element 400 of FIG. 4 are J, K, L, M, Jh, Lh, and the Txsignals for loopback. The final outputs of element 400 are thecomplimentary values muxoutp and muxoutm. Resistive and capacitiveelements 450 and 460 may be incorporated as previously described toprovide input gain and/or frequency-dependent equalization or peaking,and resistive elements 455 provide for controllable overall gain at thefinal output stage. One or more of elements 450, 455, and 460 may betrimmable or adjustable, and/or may include capacitive values of zero ifno frequency dependency is desired. One or more of load resistors shownas 415, 416, and 417 may be replaced by current sources, by currentsources controlled by a common mode feedback, or by a combination of aresistor and inductor to provide additional high-frequency peaking.

An alternative embodiment of 400 is shown in FIG. 7 with all inputmultiplexing taking place in a single stage, rather than in the cascadedstages of FIG. 4. Cascode transistors 790 are shown as an optionaladdition to provide additional isolation of the half-level inputs (andtheir associated circuit parasitic capacitance) when not enabled bycontrol Enab13. As with the previous example, resistors 750 andcapacitors 760 may be utilized to adjust gain and/or high frequencypeaking or compensation, and may be trimmable or adjustable. Loadresistors 715 may also be replaced by current sources, by currentsources controlled by a common mode feedback, or by a combination ofresistors and inductors to provide additional high-frequency peaking.

Receive Input System for Vector Signaling Code

The previously described circuits may be combined to produce a completereceive input system, as shown in the block diagram of FIG. 5. As anexample, four chip-to-chip interconnection wires labeled as inputs a, b,c, d may be terminated as previously described for FIGS. 3A-3C bytermination network 300.

Three instances of combined multiplexer and computation element 400 areused, each operating as previously described, e.g., for FIG. 4. Thethree instances of element 400 shown in FIG. 5 as 520, 530, and 540respectively perform the computations associated with Equation 3,Equation 4, and Equation 5, based on the permutations of input signalconnections shown. Under control of signals MuxSel (which within element400 manipulate controls Enable1 through Enable7 of FIG. 4 as previouslydescribed) instance 520 may also alternatively provide a differentialresult of inputs a and b, a differential result of attenuated inputsignals ah and bh, or a loopback of internal signals Txa and Txb.Similarly, instance 540 may also alternatively provide a differentialresult of inputs c and d, a differential result of attenuated inputsignals ch and dh, or a loopback of internal signals Txc and Txd, andinstance 530 may alternatively provide a loopback of internal signalsTxe and Txf.

In one embodiment, the outputs of instance 530 are used only innon-legacy, non-loopback modes, thus the unused signal inputs of 530 areconnected to a passive signal level such as ground. Although onefamiliar with the art would note that the instance of 530 could besimplified by removing unnecessary components associated with the unusedfunctions, the amount of chip area wasted by not doing so is extremelysmall, while maintaining identical layouts for all instances providesconsistent loading and delay characteristics throughout.

Other Variations

In at least one embodiment, all active transistor stages (e.g., of thecircuit of FIG. 4 or the system of FIG. 5) are biased to besubstantially in linear amplification mode. Thus, as examples, thesignal outputs muxout0 p, muxout1 p, muxout2 p, etc. of FIG. 5 representanalog signals, albeit ones that uniquely identify code words of thevector signaling code. Subsequent reception steps may include additionalfrequency- or time-domain equalization, sampling to capture particulartime intervals, and slicing to obtain digital results. However, thepossibility of incorporating such subsequent steps is not limiting; aminimal embodiment may utilize, as examples, simple threshold (e.g.,Schmidt trigger) gates or high gain nonlinear amplifier stages toconvert the outputs to digital values.

FIG. 6 provides a block diagram of another embodiment, incorporatingfeedback around the multiplexer and VGA stages to extend frequencyresponse and allow greater receive bandwidth.

For purposes of illustration, the previously-described components of thereceive detection system are shown in FIG. 6 as representinginput/computational element 610 acting on inputs 601 and 611 acting uponinputs 602, multiplexer element 620 selecting between theinput/computational elements, and output amplifier 630 producing signaloutputs 650. As examples suggested by the symbols on their icons, 610and 611 may further incorporate frequency-dependent peaking or filteringaction, and 630 may further incorporate adjustable gain. Portions ofoutputs 650 are passed through networks comprised of resistors 631 andcapacitors 632 to amplifiers 640, creating a controlled negativefeedback loop that extends the linearity and bandwidth of includedelements 620 and 630. As suggested by 632, elements of the feedbacknetwork may be adjustable or trimmable.

Other embodiments in accordance with the invention may interface tovoltage-mode or high-impedance unterminated signal inputs, and/orcommunicate internal signals as voltage rather than current levels. Suchembodiments may incorporate the known practice of using transmissiongates as multiplexing elements.

The examples illustrate the use of vector signaling codes forpoint-to-point wire communications. However, this should not been seenin any way as limiting the scope of the described invention. The methodsdisclosed in this application are equally applicable to othercommunication media including optical and wireless communications. Thus,descriptive terms such as “voltage” or “signal level” should beconsidered to include equivalents in other measurement systems, such as“optical intensity”, “RF modulation”, etc. Similarly, specific examplesprovided herein are for purposes of description, and do not imply alimitation.

As used herein, “physical signal” includes any suitable behavior and/orattribute of a physical phenomenon capable of conveying information. Inaccordance with at least one embodiment of the invention, physicalsignals may be tangible and non-transitory. In accordance with at leastone embodiment of the invention, interpreting a set of signals asselecting an object (e.g., a data object) includes selecting the objectbased at least in part on the set of signals and/or one or moreattributes of the set of signals. In accordance with at least oneembodiment of the invention, interpreting a set of signals asrepresenting an object (e.g., a data object) includes determining and/orselecting the object based at least in part on a representationcorresponding to the set of signals. In accordance with at least oneembodiment of the invention, a same set of signals may be used to selectand/or determine multiple distinct objects (e.g., data objects).

What is claimed is:
 1. A method comprising: obtaining a set of inputsignals via respective wires of a multi-wire bus; generating a set ofcomparator outputs at a set of multi-input comparators (MICs) in a firstmode of operation, each MIC having an associated input permutation of aplurality of input permutations associated with a vector signaling code,each MIC generating a respective comparator output by forming acomputation of the plurality of input signals according to theassociated input permutation; and generating at least two differentialoutputs at the set of MICs in a second mode of operation, eachdifferential output generated by comparing signal values of inputsignals obtained on a respective pair of wires of the multi-wire bus. 2.The method of claim 1, further comprising obtaining a selection signalto configure the set of MICs to operate in the first or second mode ofoperation.
 3. The method of claim 2, wherein configuring a correspondingMIC of the set of MICs to operate in the second mode of operationcomprises disconnecting signals that are not in the respective pair ofwires from the corresponding MIC.
 4. The method of claim 2, wherein theselection signal disables at least one MIC of the set of MICs in thesecond mode of operation.
 5. The method of claim 1, wherein at least oneof the comparator outputs is generated by a computation of at leastthree input signals of the set of input signals.
 6. The method of claim5, wherein each comparator output is generated by a computationincorporating all of the input signals of the set of input signals. 7.The method of claim 1, further comprising attenuating the set of inputsignals in the second mode of operation.
 8. The method of claim 1,wherein the set of MICs generate three comparator outputs in the firstmode of operation and two differential outputs in the second mode ofoperation.
 9. The method of claim 1, wherein the set of MICs generatethe set of comparator outputs on a differential output node via aplurality of differential pairs of transistors, each transistorreceiving a respective input signal of the set of input signals.
 10. Themethod of claim 9, wherein each transistor in the plurality ofdifferential pairs of transistors are biased in a linear amplificationmode.
 11. An apparatus comprising: a multi-wire bus configured toprovide a set of input signals, each input signal of the set of inputsignals provided via a respective wire of the multi-wire bus; and a setof multi-input comparators, each MIC having an associated inputpermutation of a plurality of input permutations associated with avector signaling code, the set of MICs configured to: generate a set ofcomparator outputs in a first mode of operation, each comparator outputgenerated by a corresponding MIC forming a computation of the pluralityof input signals according to the associated input permutation; andgenerate at least two differential outputs in a second mode ofoperation, each differential output generated by comparing signal valuesof input signals obtained on a respective pair of wires of themulti-wire bus.
 12. The apparatus of claim 11, wherein the set of MICsreceive a selection signal for configuring the set of MICs to operate inthe first or second mode of operation.
 13. The apparatus of claim 12,wherein the selection signal is configured to disconnect signals thatare not in the respective pair of wires from the corresponding MIC inthe second mode of operation.
 14. The apparatus of claim 12, wherein atleast one MIC of the set of MICs is disabled in the second mode ofoperation.
 15. The apparatus of claim 11, wherein at least one MIC ofthe set of MICs forms a computation of at least three input signals ofthe set of input signals.
 16. The apparatus of claim 15, wherein eachMIC of the set of MICs forms a computation incorporating all of theinput signals of the set of input signals.
 17. The apparatus of claim11, further comprising an attenuation circuit configured to attenuatethe set of input signals in the second mode of operation.
 18. Theapparatus of claim 11, wherein the set of MICs is configured to generatea set of three comparator outputs in the first mode of operation and togenerate two differential outputs in the second mode of operation. 19.The apparatus of claim 11, wherein each MIC of the set of MICs comprisesa plurality of differential pairs of transistors connected to adifferential output node, the plurality of differential pairs oftransistors receiving the set of input signals according to theassociated input permutation.
 20. The apparatus of claim 19, whereineach transistor in the plurality of differential pairs of transistorsare biased in a linear amplification mode.